Open access peer-reviewed chapter

# NFC Sensors Based on Energy Harvesting for IoT Applications

By Antonio Lazaro, Marti Boada, Ramon Villarino and David Girbau

Submitted: May 20th 2019Reviewed: August 21st 2019Published: October 2nd 2019

DOI: 10.5772/intechopen.89283

## Abstract

The availability of low-cost near-field communication (NFC) devices, the incorporation of NFC readers into most current mobile phones, and the inclusion of energy-harvesting (EH) capabilities in NFC chips make NFC a key technology for the development of green Internet of Things (IoT) applications. In this chapter, an overview of recent advances in the field of battery-less NFC sensors at 13.56 MHz is provided, and a comparison to other short-range RFID technologies is given. After reviewing power transfer in NFC, recommendations for the practical design of NFC-based sensor tags and NFC readers are made. A list of commercial NFC integrated circuits with energy-harvesting capabilities is also provided. A survey of recent battery-less NFC sensors developed by the group including soil moisture, water content, pH, color, and implanted NFC sensors is done.

### Keywords

• battery-less
• near-field communication (NFC)
• energy harvesting
• implantable medical devices
• wireless power transfer (WPT)
• internet of things (IoT)

## 1. Introduction

In recent years, radio identification (RFID) technology [1, 2] has grown extraordinarily. Initially, it came to replace barcodes for product identification [3]. Nowadays, there are several frequency bands and a number of applications [2]. RIFD can be classified depending on the frequency band used: low frequency (LF), high frequency (HF), ultrahigh frequency (UHF), or microwave bands [2]. Another classification refers to the power source: tags can be passive if they harvest the energy from the RF interrogating signal of the reader or active if the energy to feed the electronics is obtained from a battery. The communication in passive tags is based on backscattering communication and consists on modulating the load that modifies the radar cross section of the antenna [4, 5]. Although UHF readers are expensive (1–2 k$), the inlays designed for traceability are cheap, and the return on investment (ROI) is possible due to the large number of units involved. The read range can be increased by improving the IC sensitivity (e.g., −22 dBm for Impinj Monza R6) allowing to reach several meters (about 10–15 m). There exist also semi-passive or battery-assisted tags (BAP) that use battery to feed only the electronics needed to improve the sensitivity, but the communication is based on backscattering as in the passive tags [6, 7, 8]. The cost of UHF BAP tags is often lower than active tags based on transceivers such as Bluetooth low energy (BLE), Zigbee, etc. Recently, several UHF BAP transponders have appeared in the market such as the AMS-SL900A IC [7, 9]. This chip integrates a 10-bit ADC and an internal temperature sensor. However, the sensitivity in passive mode (without battery) is lower (−6.9 dBm) than the BAP mode (−15 dBm) that allows a longer rad range and data logging [7]. Semi-passive tags are microwave frequencies, or zero power tags are recently under intense research for sensing [10, 11]. At LF and HF, the radio link is established by near-field communication (NFC) because the distance is smaller than the wavelength. Therefore, the tag is in the near-field region, and the magnetic field decays proportionally to the square of the distance. Therefore, the communication between the loop antennas of the reader and the tag is produced by inductive coupling. However, at UHF and microwave bands, the communication is based on the modulation of the far fields, and hence the electromagnetic fields decrease and become inversely proportional to the distance. As a result, the read range of these tags is higher than those based on near-field communication [2, 4, 5]. Another recent approach to radio identification is the one known as chipless RFID [12, 13]. In these tags, the identification is done without a chip by a permanent modification of the structure that determines a specific electromagnetic signature in the frequency domain [12, 13, 14, 15] or in the time domain [16, 17]. Initially, the main research efforts have been oriented to increase the number of bits that the electromagnetic structure can encode [13]. In frequency-coded chipless RFID, the number of bits is limited by the number of resonators with high-quality factors that can be integrated and detected in the bandwidth [13]. In time-coded chipless RFID, the number of bits is encoded in the length of the line, and it is limited by the time domain resolution of the radar that depends on its bandwidth and the losses of the lines [5]. The most important drawback of this technology is the detection of the tags. The change in the radar cross section (RCS) introduced by the chipless tag in frequency domain or in time domain is small compared with the clutter and objects in which the tag is attached. Therefore, in order to detect the tag, the background subtraction technique is often used in the literature. This technique consists of the subtraction of the background from the measurements using a previous saved measurement without the presence of the tag. In addition, the small perturbations introduced for the tag requires highly sensitive receivers; therefore, expensive vector network analyzers (VNAs) are often used as readers [18]. Another important drawback is the detection of several chipless tags in a small area due to the inexistence of an anti-collision protocol. The tags can only be identified by time gating if their spacing is higher than the spatial radar resolution [19] that is the function of the reader bandwidth. In order to mitigate these important issues, depolarizing tags [20] that reduce the clutter contribution and improve detection techniques have been developed in the literature [5, 21, 22]. In spite of these advances, the read range in frequency-coded chipless RFID is about 0.5–1 and 2–3 m for time-coded chipless tags. The inexistence of standardized readers in the market [18] and the limitations in the number of identification codes [13], in the read range, and in the cost (because it often uses high-frequency substrates, much more expensive than the substrates used in the inlay tags) are nowadays the challenges of this approach compared to UHF or other well-established RFID technologies. However, the interest of sensors based on chipless technology [23, 24, 25, 26] is recently growing in those cases in which the robustness to harsh environments [26, 27] and the cost may be competitive with other sensor technologies. In sensor applications, the anti-collision issues are not critical in those applications in which the number of sensors is small, and few bits can be used for identification or other techniques can be employed. Small number of resonators can be used for identification, and other resonators can be dedicated for sensing. The small number of resonators in chipless sensors simplifies its detection too and the bandwidth requirements [28]. Near-field communication technology at 13.56 MHz [29] is massively used for payment systems using NFC cards. Consequently, most smartphones include an NFC reader as it is shown in the exponential growing of number of NFC-enabled mobile devices depicted in Figure 1 [30]. NFC employs electromagnetic induction between two loop antennas; therefore the range of these tags is constrained by the rapid drop of the magnetic field with the distance. However, enough energy can be harvested to feed low-power microcontrollers and sensors. As a consequence, the interest in the market of NFC-based sensors [31] is growing. Recently several manufacturers of NFC integrated circuits include the possibility of using energy harvesting (EH) in these integrated circuits. These components provide up to 3 mA at 2–3 V to feed low-power sensors [32]. These battery-less sensors can be interesting in numerous applications for short-range wireless reading of low-cost sensors. The use of mobiles as a reader for standardized tags enables a fast introduction of these sensors in the market. On the other hand, batteries contain toxic components that can contaminate foods and release waste pollutants to the environment [33]. Therefore, the use of battery-less sensors is a preferable choice in applications in which the devices are in contact with food or implanted in the body. In addition, in this last case, the replacement of the batteries is an important drawback. Nowadays, besides the traditional applications of identification, the interest of RFID technology in applications such as sensing [34] and localization [35, 36] (e.g., for robot guidance) is growing. Table 1 summarizes the main properties of passive RFID used for sensing (chipless RFID, NFC, UHF, and RFID) and a BLE as a representative wireless technology used in modern wearable applications. The key features of RFID technologies over active wireless technologies (such as Bluetooth or Zigbee) are the cost and the short setup time due to simpler communication protocol. The absence of battery, or its long lifetime in the case of BAP tags, is another valuable feature of the RFID technology. Depending on the read range required, NFC or UHF can be used. Nowadays, chipless RFID is a promising technology for short-range sensing. However, it is not mature enough for commercial use yet. Advanced sensors require additional processing; therefore, active wireless communication technologies with integrated microcontroller are needed. For wearable applications, BLE is a good option because this technology is available in smartphones. The cost of the reader is another important point that determines the selection of the technology. While the NFC and Bluetooth are low cost because most of the smartphones are equipped with NFC and Bluetooth modules, UHF readers are expensive, and therefore this technology is used in professional or logistic users but not for personal applications. In sensing applications where the read range of the Bluetooth is limiting, other wireless communication technologies such as Wi-Fi, Zigbee networks for medium range, or GPRS, Sigfox, LoRa, or NB-IoT for long range can be considered [37]. FeatureChipless RFIDNFCUHF RFIDBLE Communication methodBackscattering far fieldBackscattering near fieldBackscattering far fieldTransceiver far field Read rangeTypically, <50 cm for frequency-coded 2–3 m for time-coded UWB 1–2 cm for proximity cards with energy harvesting, 0.5 m for vicinity cardsUp to 15 m with inlay tags with −22 dBm read IC sensitivity Up to 3 m UHF sensors (with −9 dBm read IC sensitivity) Up to 30 m BAP About 10 m Energy sourcePassivePassive or semi-passivePassive or semi-passiveActive Tag priceModerateLowLowHigh Reader costHigh, no commercialLow, smartphoneHigh 1–2 k$Low, smartphone
StandardNoYesYesYes
Universal frequency regulationNo, often used UWBYes, ISMNo, by regionsYes, ISM
Tag sizeLargeMediumMediumSmall
Memory capacity<40 bits<64 kbits96bits EPC, typically 512 bits for users (<64kbytes)Several Kbytes depending on the microcontroller
ID rewritableNoYesYesYes
Setup timeLess than 0.1 sLess than 0.1 sApprox. 6 s
Energy harvestingNoApprox. 10 mWFew μWNo
Tag substrateLow-loss microwave substratesLow cost or FR4Low cost or FR4FR4
Tag flexibilityDepends on the substrateDepends on the substrateDepends on the substrateNo
Tag robustnessHighLow (inlays)Low (inlays)Moderate

### Table 1.

Comparison of RFID technologies [32].

## 2. NFC energy harvesting

### 2.1 NFC communication

NFC employs electromagnetic induction between two loop antennas. It operates within the globally available unlicensed radio frequency ISM band of 13.56 MHz on ISO/IEC 18000-3 air interface at rates ranging from 106 to 424 kbit/s [2]. The communication between reader and tag is briefly described in Figure 2. Firstly, the reader transmits an unmodulated carrier to activate the tag (Figure 2a). The receiver antenna at the tag is connected to the internal rectifier, which takes energy from the RF field to power up the tag electronics. After that, the reader sends commands by ASK modulating the carrier (Figure 2b), and the internal logic at the transponder demodulates the message. The tag transponder (which is assumed to be passive) responds using the passive load modulation technique (Figure 2c), by changing its antenna impedance [2, 29]. The passive load modulation spectrum consists of the RF carrier, two subcarriers at 12.712 and 14.408 MHz, and modulated sidebands on these two subcarrier signals (Figure 3). All the transmitted data are carried in the two sidebands.

An NFC tag IC is composed by two main blocks connected to the antenna ports (see Figure 4): the wireless power transfer unit that is responsible of harvesting the energy and powering the IC and the communication unit block that demodulates the messages and generates the clock for the transmission of data back to the reader. An RF limiter to protect the IC from a high-input voltage that could damage it, a rectifier, and a shunt regulator compose the WPT unit. The load modulator can be modeled as a shunt capacitance with the antenna. The IC impedance depends on the received power mainly due to the nonlinear behavior of the rectifier and the RF limiter. Therefore, a simplified model for the tag IC consisting of a nonlinear resistance RIC in parallel with a capacitance CIC that includes the parasitic elements is considered.

### 2.2 Commercial tags IC with energy harvesting

Nowadays, the most important manufactures offer NFC IC with energy-harvesting capabilities. These ICs have access to the internal output of the rectifier to feed external circuits such as microcontrollers or sensors. Some commercial NFC ICs with energy-harvesting mode are listed in Table 2. Most of them are compatible with standards ISO14443-3 or ISO15693 and can be connected to external microcontrollers using the I2C bus or serial-to-parallel interface (SPI). The internal EEPROM memory size to store the NFC Data Exchange Format (NDEF) message varies between 4 and 64 kbit. Although most NFC ICs are designed to be connected to a microcontroller, some models such as the MLX90129 from Melexis, the SL13 from AMS, and the SIC43x from Silicon Craft integrate an A/D for autonomous sensor acquisition without an external microcontroller, reducing the part count. In addition, the model RF430FRL152H from TI integrates a low-power microcontroller (MSP430) and a 14-bit A/D. The maximum sink current that can be drawn to power external devices connected to the EH output such as sensors or microcontrollers varies with the IC model and operation mode. Most of the models can configure different current levels depending on the range of magnetic field. The current to be provided depends on field strength, antenna size, and Q factor, but it is typically limited to the order of 5 mA with output voltages between 2 and 3 V for magnetic fields of the order of 3.5–5 A/m [32].

IC model (manufacturer)Energy harvesting
Max. sink current and typical voltage
M24LR-E-R
ST25DV-I2C
(STMicro-electronics)
6 mA/3 VISO15693NoI2C4–64kBit
NT3H1101 NT3H1201 (NXP)5 mA/2 VISO14443-3NoI2C8kBit/16kBit
NF4 (EM Microelectronics)5 mA/3.6 VISO14443ANoSPI8kBit/32kBit/64KBit
GT23SC6699–1/2 (Giantec Semiconductor)NA/3.2 VISO14443-3NoI2C8kBit/16kBit
SIC4310
SIC4340
SIC4341
(Silicon Craft)
10 mA/3.3 VISO14443ANo
Yes
UART220 bytes EEPROM
AS3953A (AMS AG)5 mA/2 VISO14443A-4NoSPI1KBit
SL13 (AMS AG)4 mA/3.4 VISO15693YesSPI8 kBit temperature sensor integrated
MLX90129 (Melexis)5 mA/3 VISO15693YesSPI4kBit
RF430FRL152H (Texas Inst.)NA/3 VISO15693YesI2C/SPIMSP430
2kB FRAM

### Table 2.

Main features of some commercial NFC ICs with energy harvesting [32].

### 2.3 WPT in NFC systems and practical considerations

A simplified model of the RF front-end of an NFC reader transceiver is shown in Figure 5. The topology of the transmitter usually presents differential output, and it is connected to the loop antenna through a matching network to obtain the maximum transmitted power. The output resistance (Rout) is a function of the transmitter power, and the DC voltage determines the current consumption of the transmitter. The matching network is composed of a differential L matching network (Cs and Cp). The current that flows through the loop antenna produces the magnetic field. In order to fulfill the emission regulations, a low-pass LC filter to reduce the spurious emission at the second harmonic is included. The receiver shares the loop antenna with the transmitter; therefore, two series resistances Rx are often added to attenuate the signal, avoiding the AC voltage at the receiver input to exceed a limit value and saturating it. Sometimes, a capacitive splitter is used for that purpose. The input impedance of the receiver is mainly capacitive, and it is modeled with the capacitance Cin in Figure 5. Although the overall impedance of the Rx and Cin is high, the effect of the receiver impedance must be considered in the design of the matching network. The steps to design this matching network can be found in [32]. In addition, recently, modern transceivers such as the ST25R391x incorporate an automatic antenna tuning method, enabling the matching network design in which Cp may be modified by switching an external bank of capacitors [38].

Printed loop antennas are used in NFC reader designs. There is a great variety of them depending on the reader type, but they are often designed to maximize the coupling with a payment card. Therefore, relatively large antennas between 4 and 5 cm square loops are integrated. The quality factor of these printed antennas is often high (more than 70). As the quality factor of the transmitter determines its bandwidth B (B = fc/Q), the quality factor (QT) must be reduced to allow the transmission of the sidebands of the carrier. To this end, two series resistances RQ are added at the input. The maximum quality factor of the transmitter is limited by the duration of the pause Tp in the modified Miller bit coding (see Figure 2):

QTmax=fc·TpE1

The quality factor is limited to 40 and 128, for standards ISO 14443 and ISO 15693, respectively (35 and 100 considering design tolerances). Condition (1) represents an additional restriction for energy harvesting compared with other WPT systems for battery charging (with or without very small communication rate) where high Q coils can be used in the transmitter and receiver to increase the power efficiency.

Despite the transmitter’s complexity, it can be modeled using a simplified Thevenin equivalent circuit tuned at fc = 13.56 MHz, used for circuit analysis (see Figure 5, right). The parasitic capacitance of the transmit antenna is included within the equivalent circuit. The relatively low-quality factor of the coils simplifies the antenna reader design. Antenna inductance varies typically between 1 and 3.5 μH. Several formulas for inductance calculation can be found depending on the shape of the printed antenna [39, 40]. In addition, the inductance and the equivalent resistance (or quality factor) can be analyzed using electromagnetic simulators such as Keysight ADS, HFSS, or CST studio, among others. The main challenge in the antenna design arises when it must be integrated into the reader case, since the proximity of metallic parts or other components (e.g., displays, batteries, or PCB boards) can modify the inductance and the parasitic capacitance. The worst case is the presence of NFC transceiver in modern smartphones, due to space limitations. Figure 6 considers three different types of reader antennas including the typical locations of the NFC antenna into the smartphone [41]. Table 3 compares the main parameters analyzed. Antenna 1 corresponds to a simple printed antenna over a PCB such as used on readers connected to PC through the USB port. Antenna 2 corresponds to a typical smartphone with a plastic case in which the antenna is attached to the battery pack of the mobile. A sheet of ferrite isolates the traces from the metal on the bottom plane. Antenna 3 is known as Murata solution [42], and it is based on the integration of the loop antenna around the hole of the camera. The magnetic field generated or collected by a coil over or close to a metallic surface is almost parallel to this surface. Hence the magnetic flux is concentrated in the proximity of the coil [43], whereas it is zero in its center because of the cancelation of the field produced by the image currents with opposite sign. The effect is a considerable reduction in the read range and the increasing of the losses. A layer of ferrite material is placed under the coil, in order to isolate the antenna in the presence of metal. Modern sintered ferrite sheets with Re(μr) between 100 and 190 and Im(μr) losses typically of 5–10 at 13.56 MHz can be found in the market (e.g., MHLL12060-000 from Laird). As it can be appreciated in Table 3, the high magnetic permeability (μr) increases the inductance depending on the thickness of the ferrite foil. The effect of the ferrite loss produces an increasing of the antenna resistance and therefore a reduction of the antenna quality factor as it can be seen in Table 3. This is not an inconvenience so that it will only be necessary to readjust the matching network. Consequently, the inclusion of a ferrite layer modifies the field boundary conditions, making the magnetic field almost perpendicular, creating a scenario similar to the case of free space [32, 44].

ParameterAntenna 1Antenna 2Antenna 3
Loop area (mm × mm)50 × 5050 × 5025 × 25
Trace width (mm)0.70.70.25
Spacing between traces (mm)0.70.70.25
Number of turns668
Substrate relative permittivity4.74.73
Substrate thickness (mm)0.80.80.1
Ferrite relative permeability*150-j5150-j5
Inductance (μH)2.683.923.63
Self-resonance frequency (MHz)77.037.479.05
Quality factor at 13.56 MHz15313274

### Table 3.

Dimensions and simulated parameters of the reader antennas of Figure 6.

100 μm thickness with 50 μm of adhesive plastic sheet of MHLL12060-200 from Laird (with μr = 150-j5) is considered.

Antenna 1 and Antenna 2 have the same dimensions, but Antenna 2 has a sheet of ferrite.

#### 2.3.2 Tag design considerations

Figure 7 shows a simplified equivalent circuit of the NFC system. The transmitter and the IC are modeled with the Thevenin model of Figure 5 and its equivalent input impedance (Figure 4), respectively. The tag antenna is modeled with an inductance L2, its equivalent resistance R2 that takes into account the antenna losses, and its parasitic capacitance Cp. The coupling between the transmitter and receiver coils allows the transfer of energy between the transmitter and the tag. In order to achieve high efficiency, the resonance frequency of the tag must be adjusted to the operation frequency (13.56 MHz).

The design of an NFC tag is relatively easy. The resonance frequency is obtained from the simplified equivalent circuit of Figure 4, and it is given by:

fr12πL2CIC+Cp+CtunE2

where L2 is the inductance of the tag antenna, CIC is the equivalent capacitance of the NFC IC, Cp is the parasitic capacitance of the antenna and interconnections, and Ctun is an additional tuning capacitance connected in parallel at the input, used to adjust the resonance frequency. CIC is nonlinear and varies about 5% with the received power. The typical values of CIC provided by the IC manufactures vary between 20 and 50 pF when low-input levels are applied on them.

Similar to the transmitter, the loaded quality factor of the tag (Q2L) must be low enough to achieve the communication bandwidth, avoiding the attenuation of the modulation of the subcarrier in the backscattering link. Therefore, the maximum value of Q2L is approximately Q2L = 8π ≈ 25 [29]. The loaded quality factor (Q2L) is the hyperbolic average of the quality factor of the tag’s antenna (Q2) and the loaded quality factor of the IC (QL). Therefore, for typical values of printed loop antennas (Q2 > 50), the loaded quality factor is approximately QL:

Q2L=11Q2+1QLQLE3
QL=RICωL2E4

Consequently, the tag quality factor Q2L < Q2Lmax if the following condition is fulfilled:

L2>RICω0Q2L,maxE5

RIC is highly nonlinear and decreases with the input level. RIC takes typical values between 1500 and 400 in commercial ICs for the activation input level [45]. Therefore, condition (5) can be easily fulfilled for tag inductances higher than 0.7 μH, and in consequence, tag design is simple because it only is necessary to tune the resonance frequency with the capacitance Ctun for the desired loop antenna.

To this end, it is important to know the environment in which the tag will be used. The presence of high-permittivity materials such as the body or, for example, on wearable or implanted applications can detune the tag. These materials are nonmagnetic; therefore, they do not modify the loop inductance, but change the parasitic capacitance, reducing the resonance frequency and increasing losses. Figure 8a shows the measured results of an implanted antenna in a phantom that consists of a piece of pork steak. The antenna is a 15 × 15 mm square coil consisting of six loops, printed in duplicates on each of the layers of a FR4 board whose thickness is 0.8 mm. The introduction of a low-permittivity cover (e.g., silicone, εr = 3) allows to reduce the losses of the phantom when the thickness is larger than 1 mm. Similar results are found for a coil close to the body surface (Figure 8b) considering a low-permittivity spacer (εr = 3) located between the coil and the body. Here the coil is a 25 × 25 mm square consisting of four loops printed on a thin flexible substrate (Ultralam 3000, thickness 100 μm).

Another typical situation is the detuning due to the presence of nearby metal surfaces. If the NFC sensor is going to work on a metallic surface, the antenna can be isolated using a ferrite foil as in the case of the reader. But the typical situation takes place in the tags that will be read by smartphones with a metallic case. In this case, the inductance of the tag will be reduced by the presence of the metal due to the opposite image currents induced on it. The result is a detuning of the tag as can be shown in Figure 9. In order to check if a tag is correctly tuned, a test coil can be connected to the port 1 of a vector network analyzer. An absorption peak will be observed at the resonance frequency if the test coil is located close to the tag (but sufficiently spaced to avoid strong coupling between the coils). Figure 10 shows the inductance of a coil as a function of the metal distance. A considerable reduction of its value is observed. Therefore, the tag must be tuned depending on the application and the desired read range of the tag.

The area available for the antenna depends on the application. For example, Table 4 shows the design of a tag sensor using the coil of Figure 10 and an M24LR04E-R IC from ST for short range (5 mm) and long range (15 mm). For long ranges (distances higher than 15 mm), the inductance and the other antenna parameters (resistance and capacitance) are nearly constant and close to the values of the free space case. The tuning capacitor (Ctun) that must be mounted in parallel at the input of the NFC IC is obtained from (2), and it is approximately 25 pF. However, for short read range applications in the presence of metal, the values of inductance for a distance of 5 mm must be considered. In this case, the tuning capacitance must be increased up to 36 pF. The inductance for each case is obtained from the measured impedance with the VNA, and the parasitic capacitance (Cp) is obtained from the self-resonance frequency of the antenna (without considering the tuning capacitor). If the antenna cannot be measured, e.g., due to the lack of laboratory instruments, the tuning capacitance can be obtained considering that the nominal inductance (value measured or computed in free space) decreases about 16% for short-range case. For very short ranges, the coupling coefficient k between the transmitter and tag antennas is very high (typically k > 0.1). Therefore, the input impedance at the transceiver increases (see Figure 7) due to the loading effect of the tag, and it is detuned because the matching network is designed considering that it is far from the reader and hence uncoupled to it. This is the reason why sometimes the tags are read worse when are on contact or very close to the reader than when are more spaced.

ParameterTuning for short range (5 mm)Tuning for long range (15 mm)
Loop area (mm × mm)50 × 5050 × 50
Trace width (mm)0.70.7
Spacing between traces (mm)0.70.7
Number of turns66
FR4 substrate thickness (mm)0.80.8
Metal thickness (μm)3434
Chip capacitance CIC(pF)27.527.5
Inductance L2 (μH)2.683.92
Self-resonance frequency (MHz)52.955.7
Antenna quality factor Q287118
Parasitic capacitance Cp (pF)2.31.7
Tuning capacitance Ctun (pF)3625

### Table 4.

Example of design for short-range application (5 mm) and long-range application (15 mm).

#### 2.3.3 WPT and read range

The communication in an NFC system can be limited by the uplink (reader to tag) when the tag does not receive enough energy to power the transponder IC or by the downlink (tag to reader) if the backscattered level received at the NFC reader is not sufficiently high to demodulate the message. For an NFC IC equipped with energy harvesting, the main limitation is the WPT in the uplink because it is necessary to provide higher energy than in a conventional NFC IC without energy harvesting. Thus, the read range in NFC tags with the EH mode activated is lower than the range for reading a previously stored data in the memory.

At this point it is interesting to take into account the factors that limit the read range of an EH NFC sensor. To this end, the wireless power transfer between the reader and tag can be analyzed considering the circuit of Figure 7. Analytical formulas found in the literature or a circuit simulator such as Keysight ADS can be used. In this model, L1 is the reader antenna inductance and R1 is its losses. C1 is the equivalent series capacitance that allows the circuit to resonate at 13.56 MHz. L1 and R1 can be obtained from the measurement of the antenna impedance or from electromagnetic simulations. Rs is the Thevenin output resistance, and it is chosen to achieve the maximum loaded Q factor in the transmitter to ensure the communication. As the reader in the smartphone is designed to read both ISO 14443A and ISO 15693 standards, the QT is often limited to 35. Therefore, Rs is obtained from the loaded quality factor of the transmitter at 13.56 MHz (Rs = ωL1/QT-R1). The inductance L2 in series with a loss resistance R2 is used to model the tag antenna.

A key parameter is the mutual inductance M between the coils, as a function of the distance. The coupling coefficient k is obtained from the Z parameters from electromagnetic simulations or S parameters measurements performed with VNA:

k=ML1L2=ImZ12ImZ11·ImZ22E6

Figure 11 compares the simulated coupling coefficient for each reader antenna as a function of the distance between the tag and reader antenna. Antenna 1 has been used as the tag antenna since it has a size similar to a smart card. The simulations have been done using Keysight Momentum. The coupling coefficient is obtained using (6) from the simulated Z parameters. Figure 11 shows a similar coupling coefficient for Antennas 1 and 2 (see Figure 6). Therefore, the introduction of the ferrite foil effectively mitigates the effect of the metal. On the other hand, the coupling coefficient of Antenna 3 (Figure 6) is smaller than in the previous cases because its area is the smallest.

The circuit of Figure 7 can be analyzed both analytically [46] or using a circuit simulator (e.g., Keysight ADS). In any case, the NFC IC is considered linear and modeled with its equivalent circuit. The values of RIC and CIC depend on the power. In addition, the manufacturer does not often give RIC. This equivalent circuit can be measured using a VNA. However, the output level of commercial VNA does not achieve the typical level in a tag under real conditions. A modified high-power VNA with an external reflectometer and a power amplifier can be used, as it is proposed in Refs. [45, 47]. An alternative setup with an oscilloscope has been recently presented in [48]. However, these setups are not often available for the users interested in the design of NFC-based sensors. In order to estimate the maximum read range, the value of RIC at that distance must be known. It can be estimated from the minimum average magnetic field, Hmin. This is the threshold average magnetic field that ensures the RF to DC conversion at the read range and can be computed from Ref. [45]:

Hmin1ffr22+1Q2L22πfμ0A·N·UminE7

where fr is the resonance frequency of the tag, A is the loop area, N is the number of loops, and Umin is the minimum AC threshold voltage at the IC input required for the NFC IC operation. Therefore, Hmin depends only on the tag parameters, and it can be considered a figure of merit of the tag. It can be experimentally found measuring the average magnetic field generated by the reader as a function of the distance between the tag and reader. A measurement procedure can be found in [32, 41]. Umin can be measured with an oscilloscope using a probe with low capacitance at the maximum distance where EH is activated.

Taking into account the coupling coefficients of Figure 11, Figure 12 compares simulated results for the antennas considered in Figure 6. It is assumed that the transmitter power is 20 dBm and that EH output is activated if the AC voltage at the input of the rectifier is high enough. In these conditions, the average field is equal to Hmin. Considering Umin = 4.8 V, Hmin = 1.2 ARMS/m, and RIC = 550 Ω, a distance between 12 and 18 mm is obtained. This estimation is in agreement with measurements of received Hav for a tag using the same antenna than in the simulation. Experimentally, a value of Hmin ≈ 1.1 ARMS/m (see Figure 13) corresponding to an EH range of 10 and 17 mm has been obtained, depending on the mobile used.

## 3. NFC sensors

Figure 14 shows the block diagram of an NFC-based data logger assisted with a complementary (optional) energy source (e.g., a solar cell). It is composed of an antenna that receives the interrogation signal emitted from a reader, usually, a mobile equipped with an NFC reader, an NFC integrated circuit, a microcontroller, and the sensor and its conditioning electronics. Table 2 shows that there are several commercial NFC ICs with energy-harvesting capabilities available in the market. These devices can operate in two modes: battery-assisted (semi-passive) and battery-less (passive). Battery-assisted devices are used in data logger applications where stand-alone continuous and autonomous monitoring is necessary. The NFC sensor is fed from a battery or assisted from an additional harvesting source. These devices can communicate with external microcontrollers using I2C or SPI interface. In the passive operation mode, the integrated NFC circuit is in charge of capturing the energy from the RF signal, rectifying it and extracting energy for the electronic circuits, microcontroller, or sensors. Sensors based on NFC IC with energy harvesting may operate in both modes: in semi-passive mode until the battery is exhausted and thereafter in passive mode. Data are stored in the EEPROM of the NFC IC to be read when the user taps the sensor. It should be highlighted that for tags in battery-less mode, data can only be updated with a new sensor reading in the presence of field from the reader. Another challenge is the amount of power that can be harvested from the RF signal. According to market research summarized in Table 2, commercial ICs can provide up to 15 mW. Despite this figure, battery-less sensors based on NFC have a wide range of applications. The most important key is that a specific reader is not required because the own smartphone equipped with NFC can be used as reader, and the data can be uploaded to cloud services using the Internet connectivity of the mobile. This fact is probably the important factor for the diffusion of this technology as can be derived from the large number of battery-less sensors based on NFC that are recently reported in the literature. Next section will review some examples.

### 3.1 Survey of NFC-based sensors

Several temperature sensors based on NFC have been proposed in the literature for different applications. In the pioneering works, based on NFC-WISP [49, 50] due to the inexistence of commercial NFC IC with energy harvesting, the rectification was performed with an external full-wave rectifier with discrete diodes. NFC-WISP communicated using the ISO-14443 protocol implemented in a low-power microcontroller (TI MSP430). As an option, the data could be shown in an E-ink display.

The monitoring of environment temperature in a cold chain or body temperature without using batteries that contain toxic products has aroused great interest. Several temperature sensors based on commercial IC such as MLX90129 [51] or RF430FRL152H [52, 53] have been reported in the literature for these applications. Other physical magnitudes can be measured with NFC sensors. For example, [54] reports a wireless tire pressure sensor based on a custom ASIC compatible with ISO14443 protocol.

A soil moisture battery-less NFC sensor for low-cost irrigation control at home, in a greenhouse, or at a garden center has been presented in [55]. The tag is based on an M24LR04E-R from ST connected to a low-cost microcontroller (ATtiny85 from Atmel). Volumetric water content of soil is obtained from capacitance measurement based on a low-power timer 555 working as an oscillator and a diode detector whose output is measured by the ADC of the microcontroller. Additionally, the temperature is measured using an I2C temperature sensor (LM75A), while air humidity is detected by reading the analog output from the HIH-5030 humidity sensor from Honeywell. The external circuitry requires less than 1 mA at 3 V to operate. Figure 15 shows an image of the soil volumetric water content sensor inserted in a flower pot, the mobile app that shows the information in the screen and a comparison between the measured and the real volumetric water content (soil moisture) [55].

A second example is a smart diaper [56]. The tag is based on the M24LR04E-R from ST and an ATtiny85 from Atmel. The microcontroller senses the capacitance between two electrodes based on the discharge time of an RC circuit. The capacitance changes as a function of the urine level, as it is shown in Figure 16. Chemical sensors inserted in NFC-based tags have also been proposed. The presence of gas sensors based on functionalized CWNT that change the resonance frequency of an NFC has also been proposed in [57].

Another advantage of NFC technology over other types of RFID working at UHF frequencies is that the NFC antennas can be designed to be compatible with the body. The effect of the body on NFC antennas is lower than at UHF band, where a considerable reduction of antenna efficiency and therefore the read range is experienced. Therefore, although the body losses reduce the quality factor of the coil and can detune the resonance frequency, the introduction of a small spacer can mitigate these effects, as shown in the previous section. Several wearable NFC-based sensors can be found in the literature that exploits this fact. In addition, the short read range inherent in the NFC technology provides a degree of privacy and security over undesired access to sensible information by nearby third parties [58, 59]. Prototypes of patches to perform measurements of body temperature based on commercial NFC IC can be found in [52, 53]. Another example is a prototype for monitoring the degree of hydration based on Melexis MLX90129 [60]. This sensor measures the concentration of NaCl in sweat, reading the surface temperature and sensing the potential difference between two electrodes. A noninvasive, NFC pH sensing system for monitoring wound healing and identifying the possibility of early-stage infection is reported in [61]. A low-power CMOS ISFET array for pH sensing is inductively powered using SIC4310 from Silicon Craft NFC IC in [62].

The authors have demonstrated that colorimetric measurements can be done with battery-less NFC. The advantage over other methods based on cameras is that the illumination conditions are similar, and therefore the measurements have higher repeatability and accuracy. A prototype of NFC colorimeter with a low-cost color light-to-digital TCS3472 converter from TAOS is integrated with an ST M24LR04E-R NFC IC and a microcontroller (see Figure 17). It is used to measure the change in color of pH tires [41]. The same method can be used for other sensors based on the measurement of the color changes due to another sensitive chemical component (e.g., urine tests). Figure 17 shows an image of the prototype and a comparison of the measured hue component as a function of the pH, showing that a simple linear model can be employed for pH calibration. The same NFC colorimeter is adapted to the design of a color-based classification system for grading the ripeness of fruit in [63] (Figure 18).

Finally, another application of NFC sensors is implantable medical devices (IMDs). Long-term implantable continuous glucose monitoring based on custom ASIC has been reported in [64, 65]. Wireless communication with IMDs is fundamental for monitoring and the reconfiguration of these devices to reduce the surgical operations [58]. Due to the size of the implanted coil, the coupling coefficient with the antennas integrated into the mobile is small, resulting in a short read range. One method to improve the readability with a modern smartphone and to increase the energy-harvesting range is including a relay coil on the body surface integrated on a patch. Figure 19a shows the setup for measuring the average magnetic field and a prototype of implanted NFC sensor integrating a LED, a temperature sensor, and a microcontroller as proof of concept (Figure 19b). Figure 20 shows the measurements with a commercial mobile of the average magnetic field as a function of the distance of an implanted coil of 15 × 15 mm within a phantom of pork steak for different depths of the implanted tag. Two systems are compared: the conventional two-coil system and a three-coil system where a relay resonant coil is on a patch over the skin. Using the last system, implanted NFC sensors can be powered by conventional smartphones at a depth up to 16 mm and read at distance between 1 and 2 cm from the skin.

## Acknowledgments

This work was supported by grant BES-2016-077291 and Spanish Government Project RTI2018-096019-B-C31.

## How to cite and reference

### Cite this chapter Copy to clipboard

Antonio Lazaro, Marti Boada, Ramon Villarino and David Girbau (October 2nd 2019). NFC Sensors Based on Energy Harvesting for IoT Applications, Recent Wireless Power Transfer Technologies, Pedro Pinho, IntechOpen, DOI: 10.5772/intechopen.89283. Available from:

### Related Content

#### Recent Wireless Power Transfer Technologies

Edited by Pedro Pinho

Next chapter

#### Dual-Band Resonator Designs for Near-Field Wireless Energy Transfer Applications

By Lai Ly Pon, Mohamed Himdi, Sharul Kamal Abdul Rahim and Chee Yen Leow

#### Optical Communication Technology

Edited by Pedro Pinho

First chapter

#### Introductory Chapter: The Path to the Future

By Pedro Pinho

We are IntechOpen, the world's leading publisher of Open Access books. Built by scientists, for scientists. Our readership spans scientists, professors, researchers, librarians, and students, as well as business professionals. We share our knowledge and peer-reveiwed research papers with libraries, scientific and engineering societies, and also work with corporate R&D departments and government entities.

View all Books