Open access peer-reviewed chapter

# Evaluation of Maximum Voltage or Maximum Link Distance on Implantable Devices

By Paulo Cesar Crepaldi, Tales Cleber Pimenta, Robson Luiz Moreno and Rômulo Mota Volpato

Submitted: December 10th 2011Reviewed: April 10th 2012Published: September 6th 2012

DOI: 10.5772/48648

## 1. Introduction

The current technology allows the implementation of electronic devices under the skin for therapeutic purposes. As a result the wireless technology can be used to monitor some illness and mitigate the patients discomfort. As an example, consider the case of diabetes patients that must undergo to daily painful blood collections to monitor the blood sugar levels. Therefore an electronic device capable of measuring the blood sugar level and transmit the result to an external device would greatly improve the quality of life of those patients. Nevertheless, the placement of an implantable device requires a minor surgery.

Once the implantable device is placed in a subject, the battery lifetime and its charge will dictate the system lifespan [1].

Consequently, it could be used the passive target technology, in which the device contains its own energy source. Thus the limitation imposed by batteries would not exist in addition to size reduction to the device. The radio frequency identification – RFID technology fits perfectly into that application.

An important parameter to be analyzed is the operation frequency. The communication frequency between the external reader and the implantable device should suffer the smallest interference due to the human tissue. The frequency of 13.56 MHz offers low attenuation and can be chosen for implantable devices. This chapter discusses the energy transfer from reader to tag by inductive coupling and its limitations. It presents a way to evaluate the target voltage provided by the inductive coupling by using basic circuit theory.

## 2. Basic inductive coupling circuit

Figure 1 shows a typical inductive coupling system. Observe that the system is composed by the reader and the tag. The reader is used to receive data from the tag and also to transfer energy to it.

It is chosen series resonance configuration, as shown in Figure 2, in order to raise the voltage at inductor L1, since voltage in a series resonance inductor is larger than the voltage provided by the source. From basic circuit theory and by observing Figure 3, the impedance seen by the reader is given as:

Z=R1+(jωL1j1ωC1)E1

The resonance, for low frequency operation, is given as:

ωL1=1ωC1.E2

However impedance Z becomes resistive and equal to R1 that represents the inductor series resistance. Therefore, the reader impedance depends on resistance R1 and voltage the inductor becomes:

E1=jIωL1=jV1ϖL1R1=jQV1.E3

At this point it is important to define the quality factor of the resonant circuit, Q=wL1/R1. It defines the ratio of stored and dissipated energy in an inductor. It demonstrates that the reader efficiency increases by using series resonance, as summarized by expression (4).

|E1|=|V1|QE4

The reader receives data and power by the inductive coupling through L1 and L2. The reader takes advantage of the parallel resonance and high impedance that occurs at frequencies near the resonance. It indicates that, at resonance, the voltage over the LC circuit is high and can be used to power up the target. Therefore the inductive coupling allows the use of passive target concept, or self-powering. Nevertheless tuned circuits have multiple resonances that cause a reduction in the energy transfer from reader to target. Thus a better understanding of the influence of resonance circuits may help to determine precisely the supply voltage at the target.

## 3. Concept of inductance

A current flowing in a straight infinite conductor generates a magnetic flow density (or magnetic induction) proportional to the current. That relationship was observed by Biot Savart, as given by (5).

B=μ04πidlXar|r|2E5

where:

dlrepresents an elemental piece of conductor,arrepresents the unit directional vector,|r|2represents the module of distance where the magnetic flow intensity is calculated,μ0is the vacuum permeability constant.

From (5), there will be a magnetic flow area around the conductor. The magnetic flow is given by (6)

ϕ=BdSE6

where:

B- represents the magnetic induction vector,dS- represents the area vector inside the magnetic induction vector.

In that line, the magnetic flow is proportional to the current flowing in the conductor and there is a linear relationship between them, known as inductance, as shown by (7).

Ldidt=dϕdtL=dϕdiE7

The premise of infinite and straight conductor of the Biot Savart law is not obeyed in the construction of inductors, thus the inductance parameter of a component will depend on many factors such as geometric shape, number of coils and resistance of the conductor.

## 4. Concept of mutual inductance

Whenever two inductors are close, the magnetic flow generated by one influences the flow in the other, as indicated in Figure 3.

Therefore, a time varying current i1 flowing on inductor 1 generates a magnetic flow 21 into inductor 2. The density of magnetic flow that reaches inductor 2 depends on the position and distance between the inductors. Thus mutual inductance is defined as the number of coils of inductor 2 that receives the magnetic flow generated by inductor 1, divided by current i1, as shown by (8).

M21=N2ϕ21i1E8

where :

1. N2 is the number of coils of inductor 2,

2. i1
3. 12 is the magnetic flow on inductor 2 due to inductor 1,

4. M is mutual inductance between inductors 1 and 2.

If there is any current on inductor 2, the same phenomenon occurs, as given by (9).

M12=N1ϕ12i2E9

Consider two inductors of length D and sectional areas A1 and A2, much smaller than D, number of coils N1 and N2 for inductors 1 and 2, respectively, and placed on the same vertical axis, as shown in Figure 4. As can be observed, inductor 1 is placed inside inductor 2 and they have the same orientation. If it is applied a current into inductor 2, the mutual inductance is given by (9).

If the magnetic field is uniform inside inductor 2, then flow 12 can be taken as (10).

ϕ12=B2A1E10

Expression (10) can be placed into (9), as:

M12=N1A1B2i2E11

By considering that the inductors core is air and the coils are composed of close and simple layers, the Biot e Savart expression can be used, where:

B2=μ0N2i2dE12

Thus, by combining (11) and (12):

M12=N1N2μ0A1dE13

From the analysis of (13) it can be observed that for the auto inductance, the number of coils is the same, thus the expression becomes:

For the inductor, the coupling will be taken in its own area, meaning that they are equal, thus:

By combining (15) and (16), one obtains:

In real case, areas A1 and A2 are not equal, indicating that the magnetic flow is not covered completely by both inductors. Therefore, the coupling factor is reduced, as given by:

M=kL1L2E18

where k is the magnetic coupling factor.

## 5. Inductive coupling with simple resonance

Although we have discussed inductive coupling between reader and target, at resonance, that characterize a double resonance, we can use simple resonance. In this configuration the reader presents just an inductor magnetically coupled to the inductor at the tag. The simplified circuit is shown in Figure 5. Observe the resonant circuit is positioned at the tag. In order to simplify the analysis, consider the circuit in free space. By considering also inductors without loss, the circuit of Figure 5 can be equated by using (2), resulting into (19) and (20).

V1=I1jϖL1I2jϖME19
0=I2(jϖL2+1jwC2)I1jϖME20

where M is the mutual inductance between inductors L1 and L2.

From (20):

I2=I1jϖMjϖL2+1jϖC2E21

By replacing (18) into (21):

I=2I1jϖkL1L2jϖL2+1jϖC2E22

Now, replacing (22) into (19):

V1=I1jϖL1I1jϖkL1L2jϖkL1L2jϖL2+1jϖC2E23

Thus, the impedance seen by the generator is:

Z1=V1I1=jϖL1+ϖ2k2L1L2jϖL2+1jϖC2E24

From the analysis of (24), it can be observed that the inductance seen by the reader is inductance L1 added to impedance Za reflected from the target, and represented by:

Za=ϖ2k2L1L2jϖL2+1jϖC2E25

Therefore, by using the same analysis, the impedance Zb reflected on inductor L2 is:

Zb=ϖ2k2L1L2jϖL1E26

The equivalent circuit reflected at the target is shown in Figure 6.

By considering the equivalent circuit at resonance, then:

0=(jϖL2+ϖ2k2L1L2jϖL1+1jϖC2)I2E27

From the development of (27):

0=jϖL2(1k2)+1jϖC2E28

From (28), the resonance frequency is given as:

Fo1=12πL2(1k2)C2E29

Thus the resonance frequency at the target was modified by the term r given by:

r=11k2E30

Consequently, the resonant frequency varies according to the coupling factor k. Thus, the distance between the inductors and their relative orientation can modify the amount of energy transferred by the inductive coupling. In order to validate equation (29), it was run a Spice simulation with a coupling factor ranging from 0.1 to 0.3, as shown in Figure 7. It can be observed that resonance frequency increases along with the coupling factor. As an initial condition, L1 and L2 were taken as 3,5 H and capacitor C1 equals to 38 pF. Observe, from Figure 7, that voltage on inductor L increases along with the coupling factor.

## 6. Inductive coupling with double resonance

There are two tuned circuits in the double resonance, where the primary is the reader and the secondary is the tag. Figure 8 presents the basic configuration for the double resonance inductive coupling.

From the analysis of Figure 8 and by considering free space and inductors without loss, then:

V1=I1(jϖL1+1jϖC1)I2jϖME31
0=I2(jϖL2+1jϖC2)I1jϖME32

From (32) it can be obtained that:

I2=jϖMI1jϖL2+1jϖC2E33

By replacing (33) into (31) one obtains:

V1=I1(jϖL1+1jϖC1)+ϖ2M2jϖL2+1jϖC2)E34

Therefore, the impedance seen by the generator is:

Z=V1I1=(jϖL1+1jϖC1)+ϖ2M2(jϖL2+1jϖC2)E35

It can be rewritten as:

Z=j{(1w2L1C1)(1w2L2C2)+w4M2C1C2wC1(1w2L2C2)}E36

Expression (36) allows the behavior analysis of the impedance at the generator, as shown in Figure 8. As previously shown, the mutual inductance depends on the coupling factor. Therefore, it can be verified the influence of the coupling factor in the response of a double tuned circuit. It was run a Spice simulation, as shown in Figure 9, where the coupling factor ranged from 0.1 to 0.2, and the frequency varied from 12 to 16 MHz. As an initial condition, L1 and L2 were taken as 3,5 H and capacitors C1 and C2 are equal to 38 pF. In that case, the resonance frequencies at primary and secondary are equal and it will be taken as an individual resonance.

From Figure 9 it can be observed that larger coupling factor causes larger deviation of the resonance frequency from the individual frequency. The energy transfer by RF coupling is directly dependent on the variation of the coupling and consequently dependent on the approaching between reader and tag, in other words orientation of the reader and tag inductances strongly changes the double resonance between reader and tag.

## 5. Mutual inductance measurement method

According to [3] and [4], the mutual inductance between two inductors can be measured. Considering two magnetically coupled inductors, as shown in Figure 10, the inductance seen by the generator is given as:

Ls'=L1+M12+M21E37

Thus, the inductance seen at the generator terminals is the inductance plus the mutual inductance of inductor 1 over inductor 2, plus the mutual inductance of inductor 2 over inductor 1. Now, considering the series association, as shown in Figure 11, the total inductance is given as:

Ls=L1+L2+M21+M12E38

If inductances L1 and L2 are associated in series, as shown in Figure 11, the resulting inductance is the sum of the individual inductance and the mutual inductances. If the measurement method is altered, as shown in Figure 12, where one inductor is inverted, the new series inductance is given as:

Ls=L1+L2M12M21E39

Now, subtracting L’ from L’’ results:

L1+L2+M12+M21L1L2+M12+M21=LsLsE40

By considering M12 = M21 =M, then:

M=LsLs4E41

Once L1 and L2 are known, the coupling factor can be found as:

k=ML1L2E42

## 6. Model for the energy transfer based on the classic circuit theory

The energy transfer between reader and tag in free space can be modeled using the classic circuit theory. Consider Figure 13 that represents the magnetic coupling between reader and tag.

Observe that resistor R2 represents the losses on L2, Rtag represents the load at the tag and R1 represents the losses at inductor L1. The analysis can be greatly simplified if the reader circuit can be converted into the series equivalent circuit, since the reader load could be represented as the resistance losses of capacitor C2. Therefore, the quality factor of capacitor C2 can be expressed in terms of its losses resistance, as indicated in Figure 14. The equivalence between series and parallel circuit is granted if the real and imaginary parts are equal, thus:

yp=Gp+jωCpE43
Rs=GpGp2+(ωCp)2E44
Cs=Gp2+(ωCp)2ω2CpE45
Gp=1RpE46

That approximation allows the conversion of tag load Rp into Rs, as given by (44). The approximation is possible since the capacitor presents low losses at the frequency range. Thus, tag load provides the larger contribution in the energy dissipation in the magnetic coupling between reader and tag.

Observe also that the equivalent capacitor given by (45) is frequency dependent that implies in another source of variation in the resonance frequency at the tag. Based on that premise, the equivalent circuit is shown in Figure 15.

The circuit of Figure 15 can be equated as:

Rt=R2+RsE47

Thus:

V1=I1(Rs+jωL1+1jωC1)I2jωME48

where M is the mutual inductance between L1 and L2.

0=I1jωM+I2(Rt+jωL2+1jωC2)E49

Combining (48) and (49) results into:

V2=V1M[(ωM)2+(Rt+jωL2+1jωC2)(Rs+jωL1+1jωC1)]C2E50

It can be observed from (5) the possibility of predicting the voltage at the tag, under free space conditions. Nevertheless, in real application, the tag shall be placed inside a human being, usually in the belly area, in order to measure any biological data. Since pork tissue presents electromagnetic properties similar to human tissue, it will be used in the measurements.

## 7. Comparison between simulated and measured data for free space

It was used the test set up shown in Figure 16, where L1 =1.77 uH and L2 =5.4uH. Observe that the inductors are axially aligned. That orientation was chosen to achieve the best magnetic coupling, considering the ratio between length and diameter of the inductor. The inductors series resistances R1 =1.14Ω and R2 =2.2 Ω (at 13.56 MHz) were obtained using a network analyzer. The experimental measurements and the simulations were conducted considering a generator having a 1V and a 50 Ω internal impedance. The tag load was taken as a 1 kΩ resistor. Table 1 presents the measurement results.

 Measurement Distance L1 - L2 M L’=10.00uHL’’=6.33uH 5mm 0.917 uH L’=9.48uHL’’=6.71uH 10mm 0.692uH L’=9.13uHL’’=7.00uH 15mm 0.532uH L’=8.74uHL’’=7.26uH 20mm 0.370uH L’=8.55uHL’’=7.40uH 25mm 0.287uH

### Table 1.

Mutual inductance measurements.

It was conducted a set of simulations of equations (44), (45) and (50) for the range of 12 to 16 MHz and the result is shown in Figure 17. It can be observed that the tag voltage is approximately 1V and the resonance frequency varied with the mutual impedance. Thus a variation in the resonance frequency will cause a change in the inductor series resistance. Therefore, in case of frequency deviation at the generator, the resistance losses can change and may alter the measurement data. As a consequence, variable capacitors C1 and C2 were added to adjust the tag voltage level at the same operation frequency. That procedure maintain the inductor characteristics regardless any frequency variation. Table 2 shows a comparison between free space measurement and simulation data.

 Distance Measured Simulated M 25mm 769mV 1001mV 0.287uH 20mm 943mV 1061mV 0.370uH 15mm 1038mV 1063mV 0.532uH 10mm 1026mV 1055mV 0.692uH 5mm 1007mV 1052mV 0.917uH

### Table 2.

Comparison between free space measurement and simulation data.

As it can be observed, there is an error between the measurement and the simulation data, as it is shown in Table 3. Note that the error is smaller than 4.3% for distances smaller than 15mm. The error becomes larger for distance over 15mm, since there is magnetic field scattering due to coil imperfections. The connection cables between generator and reader may cause a magnetic field distribution, thus increasing the error.

 Distance Error 5mm -4.3% 10mm -2.75% 15mm -2.34% 20mm -11.12% 25mm -23.17%

### Table 3.

Error between measurement and simulation data for free space.

## 8. Comparison between free space and animal tissue

Once the tag voltage for free space is known, it can be compared to implanted conditions, where there is tissue between reader and tag. Figure 18 shows the set up used for the measurements, and Table 4 provides the tag voltage comparison between free space and pork tissue conditions. Since pork tissue presents electromagnetic properties similar to human tissue, it will be used in the measurements.

 Distance Free Space Pork Tissue 10mm 1932mV 1869mV 15mm 1869mV 1787mV 20mm 1671mV 1549mV 25mm 1247mV 1202mV

### Table 4.

Comparison between free space and pork tissue data.

The generator voltage was raised to approximately 1.94V in order to assure that low voltage measurements are not spoiled by noise. The pork tissue thickness is approximately 10mm. As it can be directly observed form Table 4, the free space data is different form the pork tissue data. The small difference suggests that at 13.56MHz the pork tissue causes s variation in the magnetic permeability as compared to free space. The error between free space and pork tissue data is presented in Table 5. The 5mm measurement was not conducted due to the pork tissue thickness The first measurement, 10mm, was conducted with the reader in direct contact with the pork tissue.

 Distance Error 10mm -3.26% 15mm -4.39% 20mm -7.30% 25mm -3.61%

### Table 5.

Error between free space and pork tissue data.

## 9. Conclusions

The classic circuit theory can be used to obtain the tag voltage from the mutual inductance between reader and tag in a RFID system. Therefore, based on the estimate of the mutual inductance between reader and tag, it is possible to estimate voltage at the tag. Nevertheless the main distress is the variation on the resonance frequency due to the mutual inductance, and ultimately, the coupling factor.

Two approximations must be conducted to estimate the tag voltage. The first one is due to the magnetic scattering between reader and tag inductors that becomes more relevant as the distance between them increases. The second approximation is due to the tissue that alters the magnetic permeability and consequently reduces the tag voltage. Thus, by considering the simulation errors and the errors due to the tissue, it is possible to estimate the voltage at the tag. Table 6 presents the compiled errors.

 Distance Error 10mm -5.92% 15mm -6.66% 20mm -17.60% 25mm -26.90%

### Table 6.

Total errors between simulated and measured data.

Therefore, by taking into account both approximations it is possible to estimate the voltage drop at the tag and consequently, the power reduction. Once the power reduction is known, it can be taken into account during the tag circuit design. Consequently, the use of classic theory of magnetically coupled circuits is a simple way to estimate the voltage in implanted devices. Nevertheless additional studies regarding the resonance frequency variation is still required.

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Paulo Cesar Crepaldi, Tales Cleber Pimenta, Robson Luiz Moreno and Rômulo Mota Volpato (September 6th 2012). Evaluation of Maximum Voltage or Maximum Link Distance on Implantable Devices, Biomedical Engineering - Technical Applications in Medicine, Radovan Hudak, Marek Penhaker and Jaroslav Majernik, IntechOpen, DOI: 10.5772/48648. Available from:

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